Note: Descriptions are shown in the official language in which they were submitted.
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TITLE OF THE INVENTION
ECHO CANCELLER EMPLOYING DUAL-H ARCHITECTURE HAVING
IMPROVED NON-LINEAR ECHO PATH DETECTION
This application is a divisional application of co-pending application Serial
No.
2,307,651, filed in Canada on April 27, 2000 (International Filing Date:
November 13, 2998
from PCT/US98/24337).
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BACKGROUND OF THE INVENTION
Long Distance telephone facilities usually comprise four-wire transmission
circuits between switching offices in different local exchange areas, and two-
wire
circuits within each area connecting individual subscribers with the switching
office.
A call between subscribers in difference exchange areas is carried over a two-
wire
circuit in each of the areas and a four-wire circuit between the areas, with
conversion of speech energy between the two and four-wire circuits being
effected
by hybrid circuits. Ideally, the hybrid circuit input ports perfectly match
the
impedances of the two and four-wire circuits, and its balanced network
impedance
perfectly matches the impedance of the two-wire circuit. In this manner. the
signals
transmitted from one exchange area to the other will not be reflected or
returned to
the one area as echo. Unfortunately, due to impedance differences which
inherently
exist between different two and four-wire circuits, and because impedances
must be
matched at each frequency in the voice band, it is virtually impossible for a
given
hybrid circuit to perfectly match the impedances of any particular two and
four-wire
transmission circuit. Echo is, therefore. characteristically part of a long
distance
telephone system.
Although undesirable, echo is tolerable in a telephone system so long as the
time delay in the echo path is relatively short, for example, shorter than
about 40
milliseconds. However, longer echo delays can be distracting or utterly
confusing
to a far end speaker. and to reduce the same to a tolerable level an echo
canceller
may be used toward each end of the path to cancel echo which otherwise would
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return to the far end speaker. As is known, echo cancellers monitor the
signals on
the receive channel of a four-wire circuit and generate estimates of the
actual echoes
expected to return over the transmit channel. The echo estimates are then
applied to
a subtractor circuit in the transmit channel to remove or at least reduce the
actual
echo.
In simplest form, generation of an echo estimate comprises obtaining
individual samples of the signal on the receive channel, convolving the
samples with
the impulse response of the system and then subtracting, at the appropriate
time, the
resulting products or echo estimates from the actual echo on the transmit
channel.
In actual practice generation of an echo estimate is not nearly so
straightforward.
Transmission circuits, except those which are purely resistive, exhibit an
impulse response that has amplitude and phase dispersive characteristics that
are
frequency dependent, since phase shift and amplitude attenuation vary with
frequency. To this end, a suitable known technique for generating an echo
estimate
contemplates manipulating representations of a plurality of samples of signals
which
cause the echo and samples of impulse responses of the system through a
convolution process to obtain an echo estimate which reasonably represents the
actual echo expected on the echo path. One such system is illustrated in FIG.
1.
In the system illustrated in FIG. 1, a far end signal x from a remote .
telephone system is received locally at line 10. As a result of the previously
noted
imperfections in the local system. a portion of the signal x is echoed back to
the
remote site at line 15 along with the signal v from the local telephone
system. The
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echo response is illustrated here as a signal s corresponding to the following
equation:
s=x*h
where h is the impulse response of the echo characteristics. As such, the
signal sent
from the near end to the far end, absent echo cancellation, is the signal y,
which is
the sum of the telephone signal v and the echo signal s. This signal is
illustrated as
v at line 15 of FIG. 1.
To reduce and/or eliminate the echo signal component s from the signal y,
the system of FIG. 1 uses an echo canceller having an impulse response filter
h that
is the estimate of the impulse echo response h. As such, a further signal s'=
representing an estimate of echo signal s is generated by the echo canceller
in
accordance with the following equation:
s==h*x
The echo canceller subtracts the echo estimate signal S' from the signal y to
generate a signal e at line 20 that is returned to the far end telephone
system. The
sigiial e thus corresponds to the following equation:
e=s+v - s ::V v
As such, the signal returned to the far end station is dominated by the signal
v of the
near end telephone system. As the echo impulse response h more closely
correlates
to the actual echo response h, then s more closely approximates s and thus the
magnitude of the echo signal component s on the signal e is more substantially
reduced.
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The echo impulse response model h may be replaced by an adaptive digital
filter having an impulse response h. Generally, the tap coefficients for such
an
adaptive response filter are found using a technique known as Normalized Least
Means Squares adaptation.
Although such an adaptive echo canceller architecture provides the echo
canceller with the ability to readily adapt to changes in the echo path
response h, it
is highly susceptible to generating sub-optimal echo cancellation responses in
the
presence of "double talk" (a condition that occurs when both the speaker at
the far
end and the speaker at the near end are speaking concurrently as determined
from
the viewpoint of the echo canceller).
To reduce this sensitivity to double-talk conditions, it has been suggested to
use both a non-adaptive response and an adaptive response filter in a single
echo
canceller. One such echo canceller is described in USPN 3,787,645, issued to
Ochiai et al on January 22, 1974. Such an echo canceller is now commonly
referred to as a dual-H echo canceller.
Another problem confronting echo canceller circuits is the possibility that
the
echo path response is non-linear. Such non-linear echo paths are often present
in,
for example, cellular telephone systems. The echo canceller must not only
respond
to the non-linear echo response to cancel the echo in an appropriate fashion,
it must
also be able to detect the presence of a non-linear response in the first
place. The
present inventors have recognized that the dual-H architecture may itself be
employed to assist in detecting a non-linear echo path to thereby signal the
echo
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canceller of the condition so that the echo canceller may respond in the
appropriate
manner.
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BRIEF SUMMARY OF THE INVENTION
An echo canceller circuit for use in an echo canceller system is set forth
that
provides sensitive non-linear echo path response detection. The echo canceller
circuit comprises a first digital filter having non-adaptive tap coefficients
to simulate
an echo response occurring during a call. A second digital filter having
adaptive tap
coefficients to simulate an echo response occurring during the call is also
used. The
adaptive tap coefficients of the second digital filter are updated over the
duration of
the call. A coefficient transfer controller is disposed in the echo canceller
circuit to
transfer the adaptive tap coefficients of the second digital filter to replace
the tap
coefficients of the first digital filter when a set of one or more transfer
conditions is
met. A non-linear echo path response detector is provided. The non-linear echo
path detector is responsive to one or more parameters of the first and second
digital
filters to detect a non-linear echo path condition.
In accordance with one embodiment of the present invention, the non-linear
echo path detector is responsive to a transfer density value corresponding to
a
number of transfers executed over a known period of time by the coefficient
transfer
controller. In accordance with a further embodiment of the present invention,
the
non-linear echo path detector is responsive to a coefficient time dispersion
characteristic of the second digital filter for detecting a non-linear echo
path
condition.
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According to a further aspect of the invention, there is provided an echo
canceller, comprising a digital filter having adaptive tap coefficients that
are updated
that simulate an echo response; a non-linear echo path detector that detects a
non-
linear echo path condition; and a time varying mode unit that places the echo
canceller in a time varying mode in response to the non-linear echo path
condition.
According to another aspect of the invention, there is provided an echo
canceller, comprising: a digital filter having adaptive tap coefficients that
are updated
to simulate an echo response; and a non-linear echo path detector that
declares a non-
linear echo path condition in response to a coefficient time dispersion
characteristic of
the digital filter.
According to a further aspect of the invention, there is provided a method for
processing an echo response, comprising simulating the echo response with
adaptive
tap coefficients; and declaring a non-linear echo path condition in response
to a
coefficient time dispersion characteristic.
According to another aspect of the invention, there is provided an echo
canceller, comprising a digital filter having adaptive tap coefficients that
are updated
to simulate an echo response; and a non-linear echo path detector that
declares a non-
linear echo path condition in response to a transfer density value
corresponding to a
transfer of the adaptive tap coefficients to a second digital filter.
According to a further aspect of the invention, there is provided a method for
processing an echo response, comprising simulating the echo response with
adaptive
tap coefficients; and declaring a non-linear echo path condition in response
to a
transfer density value corresponding to a transfer of the adaptive tap
coefficients to a
digital filter.
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BRIEF DESCRIPTION OF THE SEVERAL
VIEWS OF THE DRAWING
Figure 1 is a block diagram of a conventional canceller.
Figure 2 is a schematic block diagram of an echo canceller that operates in
accordance with one embodiment of the present invention.
Figure 3 is a flow chart illustrating one manner of carrying out coefficient
transfers in accordance with one embodiment of the present invention.
Figure 4 is a flow chart illustrating a further manner of carrying OUL
coefficient transfers in accordance with a further embodiment of the present
invention.
Figure 5 illustrates the input and output of a filter that may be used to
assist
in measuring transfer density.
Figure 6 illustrates one manner of implementing non-linear echo path
detection in the echo canceller operations previously described in connection
with
Figure 4.
Figure 7 illustrates tap coefficient time dispersion for the adaptive filter
when
responding to a linear echo path.
Figure 8 illustrates tap coefficient time dispersion for the adaptive filter
when
responding to a non-linear echo path.
Figure 9 illustrates one manner of implementing a non-linear detector using
time dispersion as applied to the echo canceller operations of Figure 4.
Figure 10 illustrates one manner of implementing an echo canceller system
employing the present invention.
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DETAILED DESCRIPTION OF THE INVENTION
Figure 2 illustrates one embodiment of a dual-h echo canceller suitable for
use in implementing the present invention. As illustrated, the echo canceller,
shown
generally at 25, includes both a non-adaptive filter h and an adaptive filter
h to
model the echo response h. Each of the filters h and h are preferably
implemented
as digital filters, such as finite impulse response (FIR) filters comprising a
plurality
of taps each having a corresponding tap coefficient. This concept may be
extended
to IIR filters as well. If FIR filters are used, the duration of each of the
FIR filters
should be sufficient to cover the duration of the echo response of the channel
in
which the echo canceller 25 is disposed.
The output of the non-adaptive filter h is available at the line 30 while the
output of the adaptive filter h is available at the line 35. Each of the
signals at lines
30 and 35 are subtracted from the signal-plus-echo signal of line 40 to
generate echo
compensated signals at lines 50 and 55. respectively. A switch 45, preferably
a
software switch, may be used to selectively provide either the output signal
at the
line 50 or the output signal at line 55 to the echo canceller output at line
60. The
switch 45 may be used to provide the echo compensation based on the h filter
during convergence and then be switched to provide the echo compensation based
on the h filter after convergence. Further, the switch 45 is directed to
provide the
echo compensation based on the h filter in response to the detection of a
double-talk
condition.
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A transfer controller 65 is used to transfer the tap coefficients of filter h
to
replace the tap coefficients of filter h. As illustrated, the transfer
controller 65 is
connected to receive a number of system input signals. Of particular import
with
respect to the present invention, the transfer controller 65 receives the
signal-plus-
echo response v and each of the echo canceller signals e and e at lines 50 and
55,
respectively. The transfer controller 65 is preferably implemented in the
software
of one or more digital sienal processors used to implement the echo canceller
25.
As noted above. the art is substantially deficient of teachings with respect
to
the manner in which and conditions under which a transfer of tap coefficients
from
h to h is to occur. The present inventors have implemented a new process and,
as
such, a new echo canceller in which tap coefficient transfers are only made by
the
transfer controller 65 when selected criterion are met. The resulting echo
canceller
25 has substantial advantaees with respect to reduced double-talk sensitivity
and
increased double-talk detection capability. Further, it ensures a monotonic
improvement in the estimates h.
The foregoing system uses a parameter known as echo-return-loss-
enhancement (ERLE) to measure and keep track of system performance. Two
ERLE parameter values are used in the determination as to whether the transfer
controller 65 transfers the tap coefficients from h to h. The first parameter,
E, is
defined in the following manner:
e
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Similarly, the parameter E is defined as follows:
E=y
e
Each of the values E and E may also be averaged over a predetermined number of
samples to arrive at averaged E and E values used in the system for the
transfer
determinations.
Figure 3 illustrates one manner of implementing the echo canceller 25 using
the parameters C and E to control tap coefficients transfers between filter h
to h.
As illustrated, the echo canceller 25 provides a default h set of coefficients
at step
80 during the initial portions of the call. After the tap coefficients values
for h
have been set, a measure of E is made at step 85 to measure the performance of
the
tap coefficient values of filter h.
After the initialization sequence of steps 80 and 85. or concurrent therewith,
the echo canceller 25 begins and continues to adapt the coefficients of h to
more
adequately match the echo response h of the overall system. As noted in Figure
3,
this operation occurs at step 90. Preferably, the adaptation is made using a
Normalized Least Mean Squares method. although other adaptive methods may also
be used (e.g., LMS and RLS).
After a period of time has elapsed. preferably, a predetermined minimum
period of time, the echo canceller 25 makes a measure of E at step 95.
Preferably,
this measurement is an averaged measurement. At step 100, the echo canceller
25
compares the value of E with the value of E. If the value of E is greater than
the
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value of E, the tap coefficients of filter h are transferred ~to replace the
tap
coefficients of filter h at step 105. If this criterion is not met, however,
the echo
canceller 25 will continue to adapt the coefficients of the adaptive filter h
at step
90, periodically measure the value of E at step 95. and make the comparison of
step 100 until the condition is met.
Although not illustrated. other transfer conditions may be imposed in
addition to the foregoing. For example. the echo canceller may impose a
requirement that a far end signal exist before a transfer may occur.
Additionally.
transfers may be inhibited during a double-talk condition. Further conditions
may
also be imposed based on system requirements.
If the echo canceller 25 finds that E is greater than E, the above-noted
transfer takes place. Additionally, the echo canceller 25 stores the value of
E as a
value Em. . This operation is depicted at step 110 of the figure 3. The value
of
E,,,,~ is thus the maximum value of ERLE that occurs over the duration of the
call
and at which a transfer has taken place. This further value is used
thereafter, in
addition to the E and E comparison, to control whether the tap coefficients of
h
are transferred by the transfer control 65 to replace the tap coefficients of
h. This
further process is illustrated at steps 115. 120. and 125 of figure 3. In each
instance. the tap coefficient transfer only occurs when both of the following
two
conditions are met: 1) E is greater than the current E, and 2) E is greater
than
any previous value of E used during the course of the call. (E is greater than
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Emac ). Each time that both criteria are met, the transfer controller 65 of
echo
canceller 25 executes the tap coefficient transfer and replaces the previous
Ema,
value with the current E value for future comparison.
Requiring that E be greater than any E value used over the course of the
call before the coefficient transfer takes place has two beneficial and
desirable
effects. First, each transfer is likely to replace the prior tap coefficients
of filter h
with a better estimate of the echo path response. Second, this transfer
requirement
increases the double-talk protection of the echo canceller system. Although it
is
possible to have positive ERLE E during double-talk, the probability that E is
greater than E,., during double-talk decreases as the value of E,n~,.
increases. Thus
an undesirable coefficient transfer during double-talk becomes increasingly
unlikely
as the value of E,n,x increases throughout the duration of the call.
The echo canceller 25 may impose both an upper boundary and a lower
boundary on the value of Ea,. For example, E,,,,, may have a lower bounded
value of 6 dB and an upper bounded value of 25 dB. The purpose of the lower
bound is to prevent normal transfers during double-talk conditions. It has
been
shown in simulations using speech inputs that during double-talk. a value of
greater
than 6 dB ERLE was a very low probability event, thus making it an appropriate
value for the initial value of Em,,, . The upper bound on E,a, is used to
prevent a
spuriouslv high measurement from setting E,n,, to a value at which further
transfers
become impossible.
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The value of E,n,, should be set to, for example, the lower bound value at
the beginning of each call. Failure to do so will prevent tap coefficient
transfers on
a new call until the echo cancellation response of the echo canceller 25 on
the new
call surpasses the quality of the response existing at the end of the prior
call.
However, this criterion may never be met during the subsequent call Thereby
causing the echo canceller 25 to operate using sub-optimal tap coefficients
values.
Resetting the Em,~ value to a lower value increases the likelihood that a tap
coefficient transfer will take place and. thereby, assists in ensuring that
the h filter
uses tap coefficients for echo cancellation that more closelv correspond to
the echo
path response of the new call.
One manner of implementing the E,,,,, value change is illustrated in the echo
canceller operations flow-chart of Figure 4. When all transfer conditions are
met
except E greater than E,,,,, , and this condition persists for a predetermined
duration
of time, the echo canceller 25 will reset the E,,,, value to. for example, the
lower
bound value. In the exemplary operations shown in Figure 4, the echo canceller
25
determines whether E is greater than the lower bound of E,,,,~ at step 140 and
less
than the current value of E,nac at step 145. If both of these condition remain
true
for a predetermined period of time as determined at step 150, and all other
transfer
criterion have been met, the echo canceller 25 resets the Em,., value to a
lower
value, for example, the lower bound of the Gm,~ value. at step 155. This lower
of
the E,,,,, value increases the likelihood of a subsequent tap coefficient
transfer.
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Choosing values for the lower and upper bound of EmaC other than 6 dB and
24 dB, respectively, is also possible in the present system. Choosing a lower
bound
of Ema., smaller than 6 dB provides for a relatively prompt tap coefficient
transfer
after a reset operation or a new call, but sacrifices some double-talk
protection. A
value greater than 6 d13, however. inhibits tap coefficient transfer for a
longer
period of time, but increases the double-talk immunity of the echo canceller.
Similarly, varying the value of the predetermined wait time T before which
E,na, is
reset may also be used to adjust echo canceller performance. A shorter
predetermined wait time T produces faster reconvergence transfers, but may
sacrifice some double-talk immunity. The opposite is true for larger
predetermined
wait time values.
A further modification of the foregoing echo canceller system relates to the
value stored as Ema, at the instant of tap coefficient transfer. Instead of
setting Ema,
equal to the E value at the transfer instant, E,,,,, may be set to a value
equal to the
value of E minus a constant value (e.g., one, three or 6 dB). At no time,
however,
should the Emõ, value be set to a value that is below the lower bound value
for
Emax . Additionally, a further condition may be imposed in that a new softened
Emax
is not less than the prior value of Ema, . The foregoing "softening" of the
Em,,.
value increases the number of transfers that occur and, further, provides more
decision-making weight to the condition of E being larger than E.
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As will be readily recognized, the echo canceller of the present invention
may be implemented in a wide range of manners. Preferably, the echo canceller
system is implemented using one or more digital signal processors to carry out
the
filter and transfer operations. Digital-to-analog conversions of various
signals are
carried out in accordance with known techniques for use by the digital signal
processors.
There are some circumstances when the foregoing transfer criterion should
be defeated. For example. the transfer criterion is preferable defeated when
1) the
long-term ERLE remains low, and 2) a small but measurable performance
advantage
of h over h is sustained over a long period of time.
One case in which it should be defeated is when the steady-state ERLE
remains below the lower value of E,na, . Such a case may occur when there is a
high-level, constant background noise entering from the near-end which may
lower
the measured ERLE considerably. Since the foregoing process prevents transfers
from occurring unless the ERLE is greater than the lower bound of Emax , no
transfers are possible in low ERLE situations. Since the h may contain the
solution
to a previous call at the start of a new, low ERLE call, defeating the
foregoing
transfer criterion is preferable in some cases.
The first condition for defeating the foregoing transfer criterion is a
sustained
low ERLE measurement over a relatively long period of time (e.g. 150 to 500
msec)
of adaptation. Since a low ERLE call will tend to have a smaller difference
between
the ERLEs of Tz and h(a 1 dB difference may be the largest difference
observed),
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the required ERLE difference between h and h for a transfer to occur should be
reduced (e.g. to 0 or 1 dB) once the long-term ERLE is confirmed to be low. To
compensate, a requirement may be imposed whereby the small ERLE difference
between h and h is maintained for a long period of time (e.g. 75 to 200 msec)
before the transfer is allowed.
Each of the filters h and h preferably include one or more D.C. taps to
compensate for non-linearities in the echo path response. The result is that
the
filters can model a D.C. shift quite accurately, and high ERLE can be achieved
despite the presence of a D.C. non- linearity.
More complex non-linearities in the echo path response generally require
more complex non-linear processing. One manner in which the echo canceller 25
can process such non-linearities is set forth in U.S. S.N. _, titled _(
Attorney
Docket No. _), the teachings of which are hereby incorporated by reference. A
further manner in which the echo canceller may compensate for non-linearities
is by
directing switch 45 to use the h filter to cancel the echo. This is due to the
fact that
the h filter is more time responsive to the non-linearities since the NLMS
adaptation process attempts to find the best short term solutions for the non-
linearities in the echo path so as to maximize ERLE even where the short term
solutions diverge from the long-term linear response.
The present inventors have recognized that a difference in the number of
coefficient transfers from h to h occurs depending on whether or not the echo
path
has a non-linear component. When the echo path has an entirely linear
response,
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the tap coefficients of h generally reflect the linear impulse response of the
echo
path. In a non-linear echo path having a non-linear residual echo signal, the
residual echo will tend to increase when compared to the linear response. In
an
attempt to reduce this residual echo, the tap coefficients of h move, for
short
periods of time, away from the linear impulse response to maximize the short-
term
ERLE. This occurs since the tap coefficients are adapted using a Least Mean
Squares adaptation process which constantly tries to minimize the short term
ERLE.
As the non-linearity of the echo signal increases, the effect of the tap
coefficients
moving away from their original linear position to gain short term
improvements
becomes more pronounced.
For linear echo paths, the operational logic of the echo canceller 25 assumes
that a number of transfers will occur at the beginning of the call as the echo
canceller 25 adjusts the taps to the model echo path response and transfers
that
model to the h filter. After the initial convergence period, the expected
number of
transfers per unit time will be become small if the echo path is truly non-
linear.
Conversely, the best cancellation solution varies with time for non-linear
calls when
using a linear echo canceller. As a result. the non-adaptive taps of the h
filter
quickly becomes sub-optimal when compared to the E value of the h filter
response. For example, the h coefficients may become sub-optimal as compared
to
h within about 50 milliseconds. As a result, the transfer density, i.e. the
number of
transfers per unit time, becomes large and continues to stay large throughout
the
entire call.
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With foregoing in mind, the echo canceller 25 measures the transfer density
after a convergence period to determine whether the echo path response is
linear or
non-linear. To this end, the echo canceller 25 is programmed to store a
transfer
density threshold value TDT. The echo canceller 25 maintains a count of the
number of transfers TC that occur over a period of time. This count is
compared to
the transfer density threshold value TDT. If this count TC. and thus the
transfer
density, exceeds the transfer density threshold value TDT. the echo canceller
25
declares the presence of non-linear echo path response and executes the
appropriate
operations needed to cancel the echo signal. If the count TC, and thus the
transfer
density, is below the threshold value TDT, the echo canceller 25 handles the
echo
cancellation as a linear echo cancellation.
The value of TC may be calculated in a number of different manners. It
may be calculated using a software counter that is read on a predetermined
periodic
basis at intervals T and that it is reset immediately after being read. The
resultine
count may be directly used and compared to the transfer density threshold
value
TDT. In such instances, the value of the transfer density threshold value TDT
is
selected based on the period used to read the software counter.
In a more complicated process for determining the value of TC, the time at
which a software counter is read and the corresponding counter value are
stored and
memory. During a subsequent reading of the counter value, both the counter
value
and the time at which the counter is subsequently read are noted. The value of
TC
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may then be calculated as the difference between the initial -and final
counter values
divided by the differences between the initial and final time values.
The value of TC may also correspond to an averaged transfer density value.
In such instances, the value TC may be calculated using a digital filter which
calculates a moving average of the number of transfer per unit time. Such a
filter
preferable has, for example, a slow attack time constant and fast decay time
constant, although this is not mandatory. A value of 1 is supplied to the
averaging
filter each time a transfer takes place during a frame having a predetermined
period.
A value of 0 is supplied to the averaging filter each time a transfer does not
take
place during the frame. When the output of the averaging filter exceeds the
threshold value TDV, a non-linear condition is declared.
Such a situation is illustrated in Figure 5. As shown, a value of 1 is applied
to the filter input during each frame in which a transfer has taken place. A
value of
0 is provided to the filter input if no transfer has taken place during the
frame. The
input value is illustrated at line 175 while the output value is illustrated
at line 180.
When this output value exceeds the threshold value TDV, designated at line
185, a
non-linear condition is declared. The foregoing filter configuration may be
implemented in hardware. However, it is preferably implemented in the software
of
one or more digital signal processors used to implement the echo canceller 25.
One manner of incorporating the foregoing threshold detection process in the
operations of the process of Figure 4 is illustrated in Figure 6. As
illustrated, the
averaging filter is notified at step 190 that a transfer has taken place. The
resulting
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filtered value is retrieved at step 195 and compared to the threshold value at
step
200. If the threshold value TDV is exceeded, the Em. value is checked at step
205
to ensure that it is above a threshold value (e.g., 12dB) before a non-linear
echo
path condition is declared. If Eis below this value, no such declaration is
made.
This check to ensure that the v value is greater than a predetermined value
assists in
ensuring that a non-linear echo path condition is not declared during periods
of
convergence and reconvergence of the adaptive filter. If is above this value,
a
non-linear echo path response is declared at step 210.
A further manner for detecting non-linearities using one or more
characteristics of the filter h is illustrated in connection with Figures 7
and 8. In
accordance with this further manner, the time dispersion of the tap
coefficient values
is used to determine whether the echo path is linear or non-linear.
A graph of the tap coefficients of the h filter with respect to the time delay
associated with each tap is illustrated in Figure 7 for a linear echo path
response.
As shown, the h response is comprised of a small number of large magnitude
taps
(shown here as those taps numbered 0 to 100) and many taps that are near 0
(shown
here as taps numbered 101 to 511), Other linear echo paths generally yield
similar
results wherein a small percentage of the total number of taps are used to
model the
echo response and a large number of taps have coefficients that are
approximately
equal to 0. As such, the h coefficients have a generally small time dispersion
value
(i.e., the majority of the energy of the h coefficients is confined to a small
window
of time).
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Figure 8 illustrates the coefficient values of h when attempting to model the
echo response of a non-linear echo path. In this case, the ratio of the number
of
taps having large tap coefficients to the number of taps having low value tap
coefficients is not as large as it was in the linear case of Figure 7. The
energy of
the taps of h is more widely dispersed among taps. The relatively lower value
tap
coefficients are much larger in the non-linear case since they are playing an
active
role in finding short-term solutions of canceling the non-linear components of
the
echo. As such, the h coefficients have a generaIIy large time dispersion value
when
attempting to model a non-linear echo path (i.e., the tap energy is dispersed
over a
large number of taps).
In view of the foregoing characteristics recognized by the present inventors.
the echo canceller 25 calculates the time dispersion of the tap coefficients
of the h
filter to determine whether the echo path is linear or non-linear. The time
dispersion value is compared to a threshold. The threshold depends on the
method
of measuring the time dispersion and can be chosen experimentally. When the
time
dispersion value moves above the threshold, a non-linear echo path is
declared.
Otherwise, the echo path is assumed to be linear. Hysteresis can be used in
making
this determination.
The time dispersion value can be calculated in many ways. In accordance
with one manner, the echo canceller may find the inverse of the fraction of
the total
tap energy which can be attributed to the largest M taps, where M is a small
number
compared to the total number of taps in the h filter. In accordance with a
further
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manner of calculating time dispersion, the echo canceller may measure the
ratio of
the L lowest tap coefficients to the number M of the largest tap coefficients.
However it is measured.. the time dispersion will be larger for non-linear
calls than
for linear calls.
The time dispersion process of the echo canceller 25 can be augmented with
a few other processes to improve its accuracy. For example, the echo canceller
25
may require that the time dispersion value remain above the threshold for a
predetermined period of time before a non-linear echo path is declared. Such a
requirement assists in preventing a period of convergence and reconvergence.
which
also might be characterized with large time dispersion values, from falsely
tripping
the non-linear detector process. Still further, the echo canceller may require
that a
measurement of the background noise be made prior to declaring a non-linear
echo
path. High levels of background noise may increase the time dispersion thereby
causing a false indication of non-linearity. The echo canceller 25 may be
programmed to require both a low background noise condition and a high time
dispersion value above the threshold before declaring the presence of a non-
linear
echo path.
One manner of implementing the time dispersion process in the process
shown in Figure 4 is illustrated in Figure 9.
When a non-linear echo path is detected, the echo canceller 25 preferably
enters a time varying mode. In this mode. the output decision logic is biased
to use
the h filter to compensate for the echo response. This may be accomplished,
for
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example, by transferring switch 45 so that the h output is consistently used
for the
echo compensation. Alternatively, this bias may be accomplished by varying the
h
to h transfer criterion discussed above so as to make the transfers more
likely to
occur. Additionally, the adaptation gain used to adapt the tap coefficients of
h is
preferably lowered so as to reduce the rate at which the tap coefficients
change and
preverit overshoot of short term solutions. Further, any split adaptation of
the tap
coefficients is inhibited in time varying mode. Such split adaptation is shown
and
described in U.S.S.N. _(Attorney Docket No. _) titled 'DUAL-H ECHO
CANCELLER HAVING SPLIT ADAPTATION OF ADAPTIVE
COEFFICIENTS," filed on even date herewith.
A further manner of detecting non-linearities based on the adapted
coefficients is to monitor the variance of each of the taps over time. A large
tap
variance indicates non-linearities while a low tap variance indicates a linear
echo
path response.
Figure 10 illustrates one embodiment of an echo canceller system, shown
generally at 700, that maybe used to cancel echoes in multi-channel
conununication
transmissions. As illustrated, the system 700 includes an input 705 that is
connected
to receive a multi-channel communications data, such as T1 transmission. A
central
controller 710 deinterleaves the various channels of the transmission and
provides
them to respective convolution processors 715 over a data bus 720. It is
within the
convolution processors 715 that a majority of the foregoing operations take
place.
Each convolution processor 715 is designed to process at least one channel of
the
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transmission at line 730. After each convolution processor 715 has processed
its
respective channel(s), the resulting data is placed on the data bus 720. The
central
controller 710 multiplexes the data into the proper multichannel format (e.g.,
T1)
for retransmission at line 735. User interface 740 is provided to set various
user
programmable parameters of the system.
Numerous modifications may be made to the foregoing system without
departing from the basic teaching thereof. Although the present invention has
been
described in substantial detail with reference to one or more specific
embodiments,
those of skill in the art will recognize that changes may be made thereto
without
departing from the scope and spirit of the invention as set forth in the
appended
claims.
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