Note : Les descriptions sont présentées dans la langue officielle dans laquelle elles ont été soumises.
D8515
VOLTAGE SEMSING AT LOADS REMOTELY
CONNECT~.D TO POWER SUPPLIES
BACKGROUND OF THE L~V~NLLON
1. Field of the Invention
The present invention relates to power supplies with
remotely located loads and more particularly to circuits
adapted for use in those supplies which sense the voltage at
the load as opposed to the output te~ninals of the supply.
2. Description of the Prior Art
In power systems the load may be located at a point
which is not physically close to the output terminals of the
supply. Such a non-physically close load will be reerred to
hereinafter by ~he term "remote"~ In every power system the
load is external to the output terminals of the supply.
Ordinarily the load will be within a few feet of the supply.
As the operating frequency of the supply increases, the
distance that the load has to be located from the supply
output terminals in order to be referred to as remote decreases.
The leads connecting the load to the supply output
terminals have both resistance and inductance which form, in
combination with any capacitance in the load, a filter. In
addition, it may also be desirable to sense the ~oltage at the
load as opposed to sensing at the output terminals of the
supply where sensing traditionally occurs. In such circum-
stances a pair of sensing leads either alone or as part of a
wiring harness is extended to the load from the supply. These
sensing leads form part of a control loop which is used to
regulate the output voltage of the supply at the load. The
filter described above, which arises from the cor,lbination of
the resistance and inductance of the leads connecting the
load to the supply output terminals and the capacitance of the
load, introduces an undesirable phase shift in this control
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loop. This phase shift may be significant depending on how
far the load is from the supply output terminals and the
operating frequency of the supply. It is, therefore, desirable
to minimize the effect that ~he undesired phase shift may have
on the voltage control loop of a power supply and in particular
those supplies that operate at a high frequency without
compromising the desirability of sensin~ the voltage at the
load. The term high frequency refers to those supplies which
operate at a frequency which is above the audible range. Such
supplies typically operate at a frequency of 20 kHz and above.
Additionally, the sense leads themselves, because of
their leng~h, may introduce erroneous signals in the form of
noise into the voltage control loop. Terminating the ends of
the sense leads at the supply with a capacitor may allow stray
a-c signals picked up in the leads to be bypassed to ground
but in turn introduces in the control loop in combination with
the resistance and inductance of the sense leads additional
undesirable phase shift. Use of sense leads which are both
shielded and in the form of a twisted pair may minimize some
o the effects that the additional undesirable phase shift
in~roduces in the control loop. While the use of such sense
leads may be effective, they do, however, add to the time for
and cost cf manufacturin~ and installing the supply. It is,
therPfore, also desirable that the effect of any additional
phase shift and noise introduced by the sense leads themselves
be minimized in a cost effective manner without compromising
the desirability of sensing the voltage at the load.
Finally, as the sense leads Pxtend some distance from
the supply to the load, they then can be subject to breakage
or accidental disconnection for any one of a number of reasons.
Upon the breaking or accidental disconnec~ion of a sense lead~
the supply output voltage may either increase or decrease from
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the regulated value. I~ile most supplies include well-known
prior art circuits to sense a relatively large undervoltage
or overvoltage condition in the supply's output voltage, it
may, therefore, be additionally desirable to detect the
S breaking of the sense lead before the output voltage reaches
the undervoltage or o~ervoltage sensing circuit threshold.
Upon the detection of such a break, a suitable alarm condition
may then be indicated.
SUMMARY OF THE INVENTION
1~ In accordance with the present invention there is
provided circuitry which senses the voltage at a load remotely
connected to the output of a power supply in order that the
supply may regulate the voltage at that load. The supply is
of the type which includes voltage re~ulating means and the
circuit of the invention has first means including leads to
sense the voltage at the load and connect the sensed voltage
to the input of the voltage regulating means. The invention
also has second means which are between the regulating means
input and the supply output to provide tight a-c coupling
between the leads and the output.
The present invention also pro~ides circuitry for
sensing a break in either one or both of the pair of leads
used to sense the voltage at the remotely connected load.
This circuit has a current source which provides a current
of predetermined polarity on the sense leads. A first detector
is connected between one of the leads and one of the output
terminals of the supply to generate a signal when that lead
is broken. A second detector is connected between the other
of the leads and the other of the output terminals to generate
a signal when the associated lead is broken.
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DESCRIPTION OF THE D~AWING
Fig. 1 is a block diagram of a typical power supply
in which the present invention may be used.
Fi~. ~ais a schematic block diagram which illustrates
one embodiment of the circuit of the present invention as
connected to the supply shown in Fig. 1 for sensing voltage
at the load.
Fig.2b is a schematic diagram of one embodiment of
the circuit of the present invention for sensing breakage in
a sense lead.
DESCRIPTION OF THE PREFERRED EMBODIMENT
Referring to Fig. 1 ther~ is shown a block diagram
for a typical high frequency power supply 20 in which the
present invention m~y be used to sense voltage at a remotely
located load 22. Supply 20 is of the type wherein a power
switch 30 is turned on and off by the use of the well-known
pulse wid~h modulation (p.w.m.) technique to thereby provide
from an input d-c voltage, designated as Vi, a regulated
output d-c volta~e, designated as Vo, having a predetermined
amplitude to the load 22. The load is located at a point
which is not physically close to the output terminals of the
supply. The operation of supply 20 is controlled as a
function of either its output voltage or current in the power
switch 30. Supply 20 includes a circuit 32 which is used to
monitor the current in the power switch 30. As is well known
in the art, it is desirable to monitor ~he current in the
power switch so as to be able to control the switching of
switch 30 in the event that excessive current should flow
therein.
The current in switch 30 may be monitored by a
transformer. The sensing transformer is conne~ted to a
circuit 34 which generates a d-c signal which is representative
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of the current being monitored. Circuit 34 then compares
that d-c signal to a predetermined re~erence signal. Circuit
34 may be embodied where power switch 30 comprises only a
single power device by the combination of a ~irst diode
having itS anode connected to one end of the secondary
winding of the monitoring transformer and its cathode connected
to the parallel combination of a resistor and a capacitor
which provides a load for the monitoring trans~ormer. The
first diode disconnects the load when the power switch is off
la to thereby allow the monitoring transformer to be reset. In
this manner energy which is stored in the transformer core
during the time the transformer is set is not dissipated
across the transformer load. Or course, when power switch 30
comprises an even number of alternately conducting power
switched devices the transformer core is automatically reset
by the alternately conducting device. In that case, circuit
34 does not have to include the ~irst diode described abbve.
A peak charging circuit, including a diode, a capacitor and
a resistor, may then be connected across the transformer load
to generate a d-c voltage representative of the current being
monitored.
The d-c signal representative of the current is stored
in the capacitor o~ the peak charging circuit and is one input
to an operational amplifier ~unctioning as an analog compara-
tor. The other input to the comparator is a d-c signal
which corresponds to a predetermined current. When the current
being monitored reaches or exceeds the predetermined amplitude,
the switching o~ the power switch is then controlled by circuit
34 to t'nereby regulate the current to the predetermined
amplitude.
Supply 20 must also monitor its output ~oltage, Vo, to
maintain regulation thereo~. A sensing circuit 40 is used to
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provide a sample of Vo to circuit 42 which compares two
voltages. One of the voltages compared by circuit 42 is
simply a voltage proportional to Vo and may be obtained by
use of a resistive volta~e dividing network havin~ Vo as its
i.nput voltage. The other voltage compared by circuit 42 is a
reference voltage which may be provided by t'ne combination of
a zener diode and a resistive network including an adjustable
resistor.
Each of the outputs of circuits 34 and 42 are provided
as inputs through OR circuit 44 to p.w.m. comparator circuit
46. The output of supply 20 is then controlled by circuit 46
as a function of either the output voltage or the current in
power switch 30. A clock circuit 54 provides the high frequency
sawtooth waveform which circuit 46 uses in its comparison.
While circuits 34, 42, 44, 46 and 54 have been shown as separate,
they may be embodied by a~ integrated circuit chip such as the
type 494 chip which is available from manufacturers such as
Texas Instru~ents or Motorola.
Sometimes it is desirable to provide circuitry which
ensures that the p.w.m. circuitry o the supply does not provide
a usable output to switch 30 until such time as the input
voltage to the supply reaches a predetermined amplitude. This
circuitry is provided in the form of input voltage detector 4
and soft start circuit 50, the output of which is connected
as another input to OR circuit 44. The input voltage to supply
20 may, for example, be provided from a d-c source such as the
bank of batteries located at a typical telephone operating
company central office or from the combination of a rectifier
and capacitor bank (not sho~m) which rectifies a-c voltage to
provide an unregulated d-c voltage therefrom.
Detector circuit 48 may, for example, be embodied by
an operational amplifier one input of which receives a
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predetermined reference voltage ~enerated from a stable source
such as a zener diode in combination with a resistive voltage
dividing network. The other input to the operational amplifier
may be cotmected by a voltage dividin~ network -to receive a
voltage representative of the input volta~e to supply 20. When
the input voltage exceeds the reference vol-tage, the operational
amplifier changes its state to provide a signal to soft start
circuit 50.
Soft start circuit 50 may be embodied, for example., by
a capacitor which prior to the change in state of the opera-
tional amplifier in circuit 48 has been held discharged by a
transistor. One end of the capacitor may be connected to a
predetermined voltage. The other end of the capacitor is
connected to the appropriate one of the inputs of the 494 chip
when the p.w.~. circuitry is so erAI~odied. .When the operational
amplifier changes states, the ~ransistor then allows the
capacitor to char~e down to common ~OV). In response thereto
the chip is activated to thereby provide a usable output to
switch 30 and associated driver circuit 52.
Supply 23 also includes a power transformer 56 whose
primary winding is connected in series combination with switch
30. Connected to the secondary winding of the transformer is
the combination of recti~ier 58 and filter 60. The rircuitry
which may be used to embody switch 30, transformer ~6, rectifier
58 and filter 60 depends on the type of switched mode power
architecture that is used for supply 20. For example, if
supply 20 uses the well-known feed ~orward or9 as it sometimes
may be called, forward converter architecture, then energy
is transferred to the load when power switch 20 is conducting.
When the switch is turned off, part of the energy which is
stored in filter 60 is transferred to the load through a
con~lutating or free-wheeling diode (not shown) which is
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connected in shunt between rectifier 58 and filter 60. P~ecti-
fier 58 may be embodied in its simplest form by a diode
connected in series with the secondary winding of transformer
56. Filter 60 may be er.lbodied in its siMplest form by an L-C
network in w~lich the inductor is in series with the rectifier
diode. It is the energy stored in the inductor which is
transferred to the load 22 during the off time of switch 30.
Referring to Fig. 2a there is shown the block schematic
diagram of a circuit 70 which is adapted for use in high
frequency supply 20 to accollplish the desirable results of
sensing at tlle remotely located load and simultaneously mini-
mizing the e~ect of any undesirable phase shifts and noise in
the voltage regulation control loop of the converter. In addi-
tion, circuit 70 also functions to detect breakage or accidental
disconnection of a sense lead~before t'ne output voltage reaches
the undervoltage or overvoltage sensing circuit threshold.
Wn~ile this circuit will be shown and described in connection
with supply 20, it should be appreciated that such a circuit
may also be used in any other high frequPncy supply which uses
leads external to the supply to ~ense the voltage at the
remote load.
The physically remote load 22 is connected to the
output terminals designated as 20a and 20b in Fig. 2a of
converter 20 by the leads designated as 21a and 21b, respectively.
As the load may be located at a point distant from tPrminals
20a and 20b, leads 21a and 21b may be quite long and this is
indicated symbolically in Fig. 2a. The output voltage, Vo,
of converter 20 appears across terminals 20a and 20b. Also
connected to the load are the leads designated as SENSE and
SENSE RETU~N which are used to sense the output voltage of
converter 20 and provide a sample thereof to the circuit 42 (see
Fig. 1) which controls the regulation of the converter output
voltage.
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More particularly, ~he SEMSE lead is connected to
circuit 42 by a resistor Rl while the SENSE RETUR~ leàd is
connected to circuit 42 by a resistor R2. Circuit 42 includes
therein various components (not shown) which function to
provide from the sens~d output voltage a voltage representative
of that output voltage and a ~ixed reference voltage. These
voltages are in turn connected to a comparator ~also not
shown) which compares the voltage representative of converter
output voltage to the reference voltage to thereby generate an
error signal at the output of circuit 42. As described
previously in connection with Fig. l, the output of circuit 42
is connected to OR'ing circuit 44 along with the outputs of
the circuits designated as 34 and 50 in that igure. For
ease of illustration, the other circuits of supply 20 between
the output of OR circuit 44 and the input of filter 60 have
been omitted from Fig. 2a. In its voltage regulation mode
of operation, converter 20 uses the signal generated by circuit
42 to control and thereby regulate its output voltage, Vo.
While specific components have not been shown in circuit 42
~or ~enerating the voltage repreQentative of the output voltage
or the reference voltage, it should be well known to those
skilled in ~he art that the representative voltage may be
~enerated by a simple xesistive volta~e divider and the
re~erence voltage may be generated by the series combination
of a resistor and a zener diode.
As described above, the SENS~ and SENSE RETURN leads
are connected by resistors Rl and R2, respectively, to circuit
42. The leads are also connected by capacitors Cl and C2,
respectively, to converter output terminals 20a and 20b.
More specificaliy, the capacitor Cl is connec~ed between the
junction designated as 70c of the resistor Rl and one input
to circuit 42 and the output terminal 20a and the capacitor
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6~D
C2 is connected between the junction designated as 70d of the
resistor R2 and the other input to circuit 42 and the output
terminal 2Ob.
It is desirable that circuit 70 minimize the detri-
mental effect of the phase shift introduced by the leads 21aand 21b and the phase shift and noise introduced by the SENSE
and SENSE RETURN leads on the voltage regulation control loop
o~ converter 20. As will now be described, it is resistors
Rl and R2 in combination with capacitors Cl and C2 which
enable circuit 70 to m;n;m; ze the effects o the undesired
phase shifts and noise. The output voltage of the converter
is a d-c voltage and the combinations of Rl and Cl and R2 and
C2 allow this voltage to be sensed at the load. In other
words, for the purposes of deriving an error signal to thereby
control the regulation of the output voltage of the converter,
the inputs to circuit 42 are connected by the SENSE and SENSE
RETURN leads to the load.
The undesired phase shift and noise are, in e~ect,
a-c disturbances and the combination of Rl and Cl and R2 and
C2 provides tight a-c coupling between the SENSE and SENSE
RETUR~I leads and terminals 20a and 20b of the converter. This
tight a-c coupling in effect makes it appear to circuit 42
that, at least with respect to a-c signals, the output voltage
of the converter is being sensed at terminals 20a and 20b.
Therefore, the effects of the undesired phase shifts and
noise which result primarily from the length of leads 21a and
21b and the SENSE and SENSE RETURN leads are m;n;mi zed in
the voltage regulation control circuitry of the converter.
This minimization is accomplished without the use of either
shielded leads and/or a twisted pair for the SENSE and SENSE
RETURN leads. While resistors Rl and R2 have been shown as
discrete components of known resistance value under certain
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circ~nstances which are dependent principally on the dls~ances
of the load from ~erminals 20a and 20b, the resistance of the
wiring used in circuit 70 may provide, without the need for
additional discrete components, the desired minimization.
Thus, circuit 70 allows the converter output voltage to be
sensed at the load and minimizes any undesired effects in the
control loop which might arise because of the distance that
load 22 is from converter output terminals 20a and 20b.
Circuit 70 also includes floating current source 68.
The source 68 is connected to the SENSE and 5ENSE RET.URN leads
at the terminals of circuit 70 designated as 70a and 70b.
Source 68 provides a relatively low amplitude d-c current to
the SENSE and SEhSE RETURN leads. Two functions result from
the use of this current source. Firstly, in a standard
re~ulating circuit containing sensing leads, when a lead
breaks the voltage between the leads attempts to Eall. The
voltage control circuitry of the supply responds to t~e fall
in voltage be~ween the leads and attempts to raise the output
voltage to thereby maintain the sensing leads at the regulated
voltage. When the current source is present, it attempts to
increase the sensing lead voltage thereby lowering the output
voltage. T~is decrease in output vol~age upon the breakage
of a sensing lead is usually more desirable for the load than
the increase of output voltage which would occur if the current
source was not present. The amount of the voltage reduction
may be limited by means of a voltage clamping device connected
between junction 70c and 70 a, and a similar device connected
between terminal 20b and junction 70d. A suitable device may,
for example, be a zener diode. In addition, in an arrangement
where conver~ers are connected in parallel, the detection of
a voltage reduction or an increase due to broken sensing
leads may be difficult because of the masking effect of the
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paralleled converter. Thus, the separate. detection circuitry
will function independently of the resultant voltage at the
output terminals.
Secondly, current source 68 is used by circuit 70 to
detect breakage of the leads. A first detector 100 has a
first inpu~ connected to the SENSE lead and a second input
connected to terminal 20a by a lead which will be referred
to hereinafter as the Vo lead. A second detector 102 has a
first input connected to the SENSE RETURN lead and a second
input ccnnec~ed to the terminal 20b by a lead which will be
referred to hereinafter as the Vo RETURN lead. Source 68 may
be implemented by any known floatin~ d-c current source
provided that it is isolated from the converter. While source
68 has been shown in Fig. 2a as a single source, it should be
appreciated that it may in fact be two current sources, each
of the same polarity as that shown for the single source. One
of the two sources is connected between the SEWSE and Vo leads
and the other of the two sources is connected between the
SENSE RETUR~ and Vo RETU~ leads.
l~en the supply is operating properly and neither of
the sense leads are broken, then (assuming that Vo is a
positive voltage~ at detector lOO the Vo lead is equal to or
more positive than the SENSE lead and at detector 102 the Vo
RETU~ lead is equal to or more negative than the SEN5E RETURN
lead. The current produced by source 68 is absorbed into load
22. When either of the sense leads break, the current fror.
source 68 that would ordinarily flow in~o that lead flows
into the respective detector. The flow of current into the
respective detector allows that detector to sense the presence
of a voltage between the broken sense lead and the associated
output lead.
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Two examples may help in a better understanding of
the operation of circuit 70 in detectin~ the breakage of a
SENSE or SENSE RETU~N lead. In each of the examples to follow
it is assumed that Vo is a positive voltage. As a first
example, assume that the SENSE lead breaks. Current from
source 68 then flows into detector 100. This flow of current
makes the terminal of detector 100 connected -to the SENSE
lead more positive than the terminal connected to the Vo lead.
The detector, there.fore, detects the presence of a voltage
between the broken SENSE lead and the Vo lead. As a second
example, assume that the SENSE RETURN lead breaks. Current
from source G8 then 1OWS into detector 102. The flow of
current makes the terminal of detector 102 which is connected
to the SENSE RETURN lead more negative than the terminal
connected to the Vo RETURN lead. The detector, therefore,
detects the presence of a voltage between the broken SENSE
RETU~ lead and the Vo RETURN lead.
Finally, while not shown ln Fig. 2a, a preload in the
form of a resistor may be connected in a manner well known in
the art across terminals 20a and 20b whenever supply 20
operates in a condition where there is no load 22 connected
to the supply. This preload aids in inhibiting any detrimental
effects that the current of source 68 might have on the no
load operation of the supply.
Referring to Fig. 2b there are shown schematic circuit
diagrams for detectors 100 and 102. The first detector 100
includes an operational amplifier which functi.ons as an analog
co~parator. The comparator, designated as Al, has its invert-
ing input connected to the current source 68 at terminal 70a
and, therefore, to the SENSE lead. The noninverting input of
the comparator is connected by a resistor R3 to a junction
lOOa. Also connected to junction lOOa is a d-c voltage, Vl,
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~2~60
which, dependent on the design of supply 20l may be either in
the first case equal to the supply output voltage, Vo, or in
th~ second case higher than Vo by the voltage drop of a series
diode connected between the capacitor in filter 60 and the
supply output.
In the ~irst case, the junction lOOa is directly
connected to the supply output terminal 20a, whereas in the
second case the junction lOOa is connected to the supply
output terminal 20a by the series diode (not shown in Fig.
2a). For either case, junction lOOa may be taken as being
equivalent to the supply output terminal. The noninverting
input terminal of the comparator is, therefore, in ef~ect
connected through R3 to the lead designated as Vo in Fig. 2a.
The noninverting input to comparator lO0 is also
connected by a resistor R4 to a source of positive voltage,
+V. The resistance of the resistor R4 is chosen to be many
times smaller than t'ne resistance of resistor R3 to thereby
provide a small bias to the noninvertin~ input of the comparator.
This small bias ensures that at the comparator the Vo lead is
~assuming Vo is a positive voltage) always more positive than
the SENSE lead for all conditions of load when supply 20
operates normally.
The second detector 102 includes an operational
a~pliier which functions as an analog comparator. The
co~parator, designated as A2, has its inverting input connected
to supply common (COM). This input is, therefore,connected in
effect to the lead designated~as Vo RETURN in Fig. 2a. The
noninver~ing input terminal of the comparator is connected by
a resistor R5 to the current source at termina~ 70b and,
therefore, to the SENSE RETURN lead. The noninverting terminal
is also connected by a resistor R6 to a source of positive
voltage, ~V. As in the case o resistors R3 and R4, described
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above, the resistance of resistor R5 is chosen to be many
times smaller than the resistance of resistor R6 to thereby
provide a small bias to the noninverting input of the
comparator. This small bias ensures that at the comparator
the SENSE RETURN lead is (assuming that Vo is a positive
voltage) always more positive than the Vo RETURN lead for all
conditions of load when supply 20 operates normally.
Detector 102 also includes a diode Dl, poled as shown,
connected between terminal 70b and the inverting input terminal
of the comparator. This diode functions to limit the amplitude
of the signal at the comparator to a range which falls within
the lnput signal amplitude specifications of the comparator.
The inverting input terminal of the comparator is connected
to output terminal 20b (COM) of the converter. The outputs
of the comparator in detectors 100 and 102 are connected
together to provide a signal to a suitably arranged alarm
cir~uit (not shown) whenever either comparator detects a
break in its associated sense lead.
The arrangement shown in Fig. 2b for detectors 100 and
102 causes the output voltage of the source to fall when a
S~NSE or SENSE RETUR~ lead breaks. Alternatively, the input
SENSE and SENSE RETURN polarities to each detector may be
reversed from those shown. In that case, the current sources
associated with the SENSE and SENSE RETURN leads must be also
reversed in polarity from that shown for source 68. In addi-
tion, it is no longer necessary for each source to be isolated
from the converter. Each of the sources may, therefore, be
more simply embodied in the manner described below. The
source associated with the SENSE lead and,therefore detector
lOO,may be embodied by connecting a current limiting resistor
(not shown) between terminal 104a and the Vo RETU~ lead.
The source associated with the SENSE RETURN lead, and therefore
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with detector 102, may be embodied also by connec~ing a
current limiting resistor (not shown) between ter~inal 70b
and the Vo lead. The current generated by each source will,
therefore, have a polarity opposite to that shown in Fig. 2b
for source 68. This opposite polarity current will cause the
output volta~e of the source to rise when either a SENSE or
SE~SE RETUR~I lead is broken.
In a circuit constructed in accordance with the present
invention, the following component values were used:
Rl = R2 = 1 x 103 ohms
Cl = C2 = 2200 microfarads
R3 = R5 = 681 ohms
R4 = P~6 = 21.1 x 103 ol~ms
l~ile the present invention has been described in
connection with the type of high frequency power supply shown
in Fig. 1, it should be appreciated that the invention is also
applicable to any type of high frequency power supply which
senses voltage at a remotely located load. It should also be
appreciated that the invention may provide an improvement in
the voltaJe sensing at remotely located loads for those power
supplies which operate at low frequency. Such low frequency
supplies typically operate in the order of 50 or 60 ~lertz. At
these low operating frequencies, the phase shift introduced in
the voltage control loop by the remote sensing is not as
detrimental to supply op~ration as the phase shift introduced
in the voltage control loop of high frequency supplies. Yet,
it may still be desirable in such low ~requency supplies to
minimize the effect that this phase shift has on supply
operation. In addition, it is always desirable,no matter at
what ~requency the supply operates, to detect breakage of a
sense lead if the supply is of the type which senses voltage
at its remotely connec-ted load.
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?
Q~
It is to be understood that the descriptions of the
preferred embodiments are intended to be only illustrative,
rather than exhaustive, of the present invention. Those of
ordinary skill will be able to make certain additions, deletions
and/or modifications to the embodiments of the disclosed
subject matter wi~hout departing from the spirit of the
invention or its scope, as defined by the appended claims.
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